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MIC23250
4MHz Dual 400mA Synchronous Buck Regulator with HYPER LIGHT LOADTM
General Description
The MIC23250 is a high efficiency 4MHz dual 400mA synchronous buck regulator with Hyper Light LoadTM. Hyper Light LoadTM provides all the advantages of standard light load modes, such as low quiescent current and high efficiency but also allows the use of very small output capacitors to maintain low output ripple voltage throughout the entire load range. This benefit is not possible with other light load mode types as they trade off control speed for low standby currents. With Hyper Light LoadTM, the output capacitor can be reduced by up to a factor of 20 saving cost and valuable board space. The tiny package (2mm x 2mm Thin MLF(R)) of MIC23250 also saves crucial board space by using only six external components while regulating two independent outputs up to 400mA each. The device is designed for use with a 1H inductor and a 4.7F output capacitor that enables a sub-1mm height. The MIC23250 has a very low quiescent current of 35A and can achieve over 85% efficiency at 1mA. At higher loads the MIC23250 provides a constant switching frequency around 4MHz while providing peak efficiencies up to 94%. The MIC23250 fixed output voltage option is available in a 10-pin 2mm x 2mm Thin MLF(R) with a junction operating range from -40C to +125C. The adjustable output voltage option will soon be available in Q2/Q3 2008. Data sheets and support documentation can be found on Micrel's web site at: www.micrel.com.
Features
* Input voltage range: 2.7V to 5.5V * Dual output current 400mA/400mA * Hyper Light LoadTM mode - 35A dual quiescent current - 1H inductor with a 4.7F capacitor * 4MHz in PWM operation * Ultra fast transient response * Low voltage output ripple - 20mVpp in Hyper Light LoadTM mode - 3mV output voltage ripple in full PWM mode * Up to 94% peak efficiency and 85% efficiency at 1mA * Fully integrated MOSFET switches * Micropower shutdown * Thermal shutdown and current limit protection * Fixed output:10-pin 2mm x 2mm Thin MLF(R) * Adjustable output:12-pin 2.5mm x 2.5mm Thin MLF(R) (Available in Q2/Q3 2008) * -40C to +125C junction temperature range
Applications
* Mobile handsets * Portable media players * Portable navigation devices (GPS) * WiFi/WiMax/WiBro modules * Digital cameras * Wireless LAN cards * USB Powered Devices ___________________________________________________________________________________________________________
Typical Application
Efficiency VOUT = 1.8V
100 VIN = 3.0V 90 VIN = 2.7V 80 70 VIN = 4.2V 60 50 40 30 20 10 0 1 L = 1H COUT = 4.7F 10 100 LOAD (mA) 1000 VIN = 3.6V
Hyper Light Load is a trademark of Micrel, Inc. MLF and MicroLeadFrame are registered trademarks of Amkor Technology, Inc. Micrel Inc. * 2180 Fortune Drive * San Jose, CA 95131 * USA * tel +1 (408) 944-0800 * fax + 1 (408) 474-1000 * http://www.micrel.com
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MIC23250
Ordering Information
Part Number Marking Nominal Output Voltage 1 1.575V 1.8V 1.0V 1.1V 1.6V ADJ Nominal Output Voltage 2 1.8V 1.2V 1.2V 0.9V 1.2V ADJ Junction Temp. Range -40 to +125C -40 to +125C -40 to +125C -40 to +125C -40 to +125C -40 to +125C Package Lead Finish Pb-Free Pb-Free Pb-Free Pb-Free Pb-Free Pb-Free
MIC23250-GFHYMT MIC23250-G4YMT MIC23250-C4YMT MIC23250-3BYMT MIC23250-W4YMT MIC23250-Adj*
Note: * Available Q2/Q3 2008
WV1 WV5 WV2 WV3 WV4 TBD
10-Pin 2mm x 2mm Thin MLF(R) 10-Pin 2mm x 2mm Thin MLF(R) 10-Pin 2mm x 2mm Thin MLF(R) 10-Pin 2mm x 2mm Thin MLF(R) 10-Pin 2mm x 2mm Thin MLF(R) 12-Pin 2.5mm x 2.5mm Thin MLF(R)
Pin Configuration
SNS1 EN1 AGND SW1 PGND 1 2 3 4 5 10 SNS2 9 8 7 6 EN2 AVIN SW2 VIN
10-Pin 2mm x 2mm Thin MLF(R) (MT) (Top View)
Pin Description
Pin Number 1 2 3 4 5 6 7 8 9 10 Pin Name SNS1 EN1 AGND SW1 PGND VIN SW2 AVIN EN2 SNS2 Pin Name Sense 1 (Input): Error amplifier input. Connect to feedback resistor network to set output 1 voltage. Enable 1 (Input): Logic low will shut down output 1. Logic high powers up output 1. Do not leave unconnected. Analog Ground. Must be connected externally to PGND. Switch Node 1 (Output): Internal power MOSFET output. Power Ground. Supply Voltage (Power Input): Requires close bypass capacitor to PGND. Switch Node 2 (Output): Internal power MOSFET output. Supply Voltage (Power Input): Analog control circuitry. Connect to VIN. Enable 2 (Input): Logic low will shut down output 2. Logic high powers up output 2. Do not leave unconnected. Sense 2 (Input): Error amplifier input. Connect to feedback resistor network to set output 2 voltage.
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Absolute Maximum Ratings(1)
Supply Voltage (VIN) .........................................................6V Output Switch Voltage (VSW) ............................................6V Logic Input Voltage (VEN) .................................. -0.3V to VIN Storage Temperature Range (Ts)..............-65C to +150C ESD Rating(3) .................................................................. 2kV
Operating Ratings(2)
Supply Voltage (VIN)......................................... 2.7V to 5.5V Logic Input Voltage (VEN) .................................. -0.3V to VIN Junction Temperature (TJ) ..................-40C TJ +125C Thermal Resistance 2mm x 2mm Thin MLF(R)-10 (JA)........................70C/W
Electrical Characteristics(4)
TA = 25C with VIN = VEN = 3.6V; L = 1H; COUT = 4.7F; IOUT = 20mA; only one channel power is enabled, unless otherwise specified. Bold values indicate -40C< TJ < +125C.
Parameter Supply Voltage Range Under-Voltage Lockout Threshold UVLO Hysteresis Quiescent Current, Hyper LL mode Shutdown Current Output Voltage Accuracy Current Limit in PWM Mode Output Voltage Line Regulation Output Voltage Load Regulation Maximum Duty Cycle PWM Switch ON-Resistance Frequency Soft Start Time Enable Threshold Enable Input Current Over-temperature Shutdown Over-temperature Shutdown Hysteresis Condition (turn-on) VOUT1, 2 (both Enabled), IOUT1, 2 = 0mA , SNS1, 2 >1.2 * VOUT1, 2 Nominal VEN1, 2 = 0V; VIN = 5.5V VIN = 3.6V, ILOAD = 20mA SNS = 0.9*VOUT NOM VIN = 3.0V to 5.5V, ILOAD = 20mA 20mA < ILOAD < 400mA, VIN = 3.6V SNS VNOM, VOUT = 1.8V, VIN = 2.7V ISW = 100mA PMOS ISW = -100mA NMOS ILOAD = 120mA VOUT = 90% Min 2.7 2.45 Typ 2.55 60 35 0.01 -2.5 0.410 0.65 0.4 0.5 86 0.6 0.8 4 260 0.8 0.1 160 40 50 4 +2.5 1 Max 5.5 2.65 Units V V mV A A % A %/V % % MHz s V A C C
80
3.4 0.5
4.6 1.2 2
Notes: 1. Exceeding the absolute maximum rating may damage the device. 2. The device is not guaranteed to function outside its operating rating. 3. Devices are ESD sensitive. Handling precautions recommended. Human body model: 1.5k in series with 100pF. 4. Specification for packaged product only.
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Typical Characteristics
50 45 40 35 30 25 20 15 10 5 L = 1H COUT = 4.7F 0.01 1 1
Quiescent Current vs. Input Voltage
10
4MHz
Switching Frequency vs. Output Current
10
4MHz
Switching Frequency vs. Output Current
L = 4.7H
VIN = 3.0V
1 L = 1H
0.1
VIN = 4.2V VOUT = 1.8V L = 1H COUT = 4.7F
L = 2.2H 0.1 VIN = 3.6V VOUT = 1.8V COUT = 4.7F 10 100 1000 OUTPUT CURRENT (mA)
0 2.7 3.2 3.7 4.2 4.7 5.2 5.7 INPUT VOLTAGE (V)
VIN = 3.6V 10 100 1000 OUTPUT CURRENT (mA)
0.01 1
5.0
Frequency vs. Temperature
1.90 1.88 1.86 1.84 1.82 1.80 1.78 1.76 1.74 1.72 1.70 1
Output Voltage vs. Output Current
4.5
VIN = 3.0V VIN = 4.2V VIN = 3.6V
1.90 L = 1H 1.88 COUT = 4.7F 1.86 1.84 1.82 1.80
Load = 10mA
Output Voltage vs. Input Voltage
Load = 1mA
4.0
3.5
3.0
L = 1H COUT = 4.7F Load = 120mA 20 40 60 80 TEMPERATURE (C)
1.78 Load = 300mA 1.76 Load = 50mA Load = 400mA 1.74
Load = 150mA
10 100 1000 OUTPUT CURRENT (mA)
1.72 1.70 2.7 3.2 3.7 4.2 4.7 5.2 5.7 INPUT VOLTAGE (V)
1.9
Output Voltage vs. Temperature
VOUT2 = 1.8V
1.2
Enable Threshold vs. Temperature
1.000 0.975
Enable Threshold vs. Input Voltage
1.0 VIN = 3.6V 0.8 VIN = 2.7V
1.8
VIN = 5.5V
0.950 0.925 0.900 0.875 0.850
Enable ON Enable OFF
1.7
L = 1H COUT = 4.7F Load = 120mA VOUT1 = 1.575V
0.6 0.4 0.2 L = 1H COUT = 4.7F 20 40 60 80 TEMPERATURE (C)
1.6
0.825
1.5
20 40 60 80 TEMPERATURE (C)
0
0.800 2.7 3.2 3.7 4.2 4.7 5.2 5.7 INPUT VOLTAGE (V)
VIN = 3.6V VOUT = 1.8V Load = 150mA
700
Current Limit vs. Input Voltage
Efficiency VOUT = 1.8V
100 VIN = 3.0V 90 VIN = 2.7V 80 VIN = 3.6V 70 VIN = 4.2V 60 50 40 30 20 10 0 1
Efficiency VOUT = 1.8V
100 90 80 70 60 50 40 30 L = 1.5H L = 1.0H
650
L = 0.47H
600 L = 1H COUT = 4.7F 5.7
550 2.7 3.2 3.7 4.2 4.7 5.2 INPUT VOLTAGE (V)
L = 1H COUT = 4.7F 10 100 LOAD (mA) 1000
20 10 0 1
VIN = 3.6V COUT = 4.7F 10 100 LOAD (mA) 1000
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Typical Characteristics (Continued)
Efficiency VOUT = 1.575V
100 VIN = 3.0V 90 VIN = 2.7V 80 70 VIN = 4.2V 60 50 40 30 20 10 0 1 L = 1H COUT = 4.7F 10 100 LOAD (mA) 1000 VIN = 3.6V 100 90 80 70 VIN = 3.6V 60 VIN = 4.2V
Dual Output Efficiency
VIN = 3.3V
50 40 VOUT1 = 1.575V 30 VOUT2 = 1.8V 20 Load1 = Load2 L1 = L2 = 1H 10 COUT1 = COUT2 = 4.7F 0 1 10 100 LOAD (mA)
1000
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Functional Characteristics
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Functional Characteristics (Continued)
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Functional Characteristics (Continued)
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Functional Diagram
MIC23250 Simplified Block Diagram
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Functional Description
VIN The VIN provides power to the internal MOSFETs for the switch mode regulator along with the current limit sensing. The VIN operating range is 2.7V to 5.5V so an input capacitor with a minimum of 6.3V voltage rating is recommended. Due to the high switching speed, a minimum of 2.2F bypass capacitor placed close to VIN and the power ground (PGND) pin is required. Based upon size, performance and cost, a TDK C1608X5R0J476K, size 0603, 4.7F ceramic capacitor is highly recommended for most applications. Refer to the layout recommendations for details. AVIN The analog VIN (AVIN) provides power to the analog supply circuitry. AVIN and VIN must be tied together. Careful layout should be considered to ensure high frequency switching noise caused by VIN is reduced before reaching AVIN. A 0.01F bypass capacitor placed as close to AVIN as possible is recommended. See layout recommendations for details. EN1/EN2 The enable pins (EN1 and EN2) control the on and off states of outputs 1 and 2, respectively. A logic high signal on the enable pin activates the output voltage of the device. A logic low signal on each enable pin deactivates the output. MIC23250 features built-in soft-start circuitry that reduces in-rush current and prevents the output voltage from overshooting at start up. SW1/SW2 The switching pin (SW1 or SW2) connects directly to one end of the inductor (L1 or L2) and provides the current path during switching cycles. The other end of the inductor is connected to the load and SNS pin. Due to the high speed switching on this pin, the switch node should be routed away from sensitive nodes. SNS1/SNS2 The SNS pin (SNS1 or SNS2) is connected to the output of the device to provide feedback to the control circuitry. A minimum of 2.2F bypass capacitor should be connected in shunt with each output. Based upon size, performance and cost, a TDK C1608X5R0J476K, size 0603, 4.7F ceramic capacitor is highly recommended for most applications. In order to reduce parasitic inductance, it is good practice to place the output bypass capacitor as close to the inductor as possible. The SNS connection should be placed close to the output bypass capacitor. Refer to the layout recommendations for more details. PGND The power ground (PGND) is the ground path for the high current in PWM mode. The current loop for the power ground should be as small as possible and separate from the Analog ground (AGND) loop. Refer to the layout recommendations for more details. AGND The signal ground (AGND) is the ground path for the biasing and control circuitry. The current loop for the signal ground should be separate from the Power ground (PGND) loop. Refer to the layout recommendations for more details.
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MIC23250 given in two methods; permissible DC current and saturation current. Permissible DC current can be rated either for a 40C temperature rise or a 10% to 20% loss in inductance. Ensure the inductor selected can handle the maximum operating current. When saturation current is specified, make sure that there is enough margin so that the peak current of the inductor does not cause it to saturate. Peak current can be calculated as follows:
1 - VOUT / VIN I PEAK = I OUT + VOUT 2xf xL
Applications Information
The MIC23250 is designed for high performance with a small solution size. With a dual 400mA output inside a tiny 2mm x 2mm Thin MLF(R) package and requiring only six external components, the MIC23250 meets today's miniature portable electronic device needs. While small solution size is one of its advantages, the MIC23250 is big in performance. Using the Hyper Light LoadTM switching scheme, the MIC23250 is able to maintain high efficiency throughout the entire load range while providing ultra-fast load transient response. Even with all the given benefits, the MIC23250 can be as easy to use as linear regulators. The following sections provide an over view of implementing MIC23250 into related applications Input Capacitor A minimum of 2.2F ceramic capacitor should be placed close to the VIN pin and PGND pin for bypassing. A TDK C1608X5R0J476K, size 0603, 4.7F ceramic capacitor is recommended based upon performance, size and cost. A X5R or X7R temperature rating is recommended for the input capacitor. Y5V temperature rating capacitors, aside from losing most of their capacitance over temperature, can also become resistive at high frequencies. This reduces their ability to filter out high frequency noise. Output Capacitor The MIC23250 was designed for use with a 2.2F or greater ceramic output capacitor. Increasing the output capacitance will lower output ripple and improve load transient response but could increase solution size or cost. A low equivalent series resistance (ESR) ceramic output capacitor such as the TDK C1608X5R0J476K, size 0603, 4.7F ceramic capacitor is recommended based upon performance, size and cost. Either the X7R or X5R temperature rating capacitors are recommended. The Y5V and Z5U temperature rating capacitors, aside from the undesirable effect of their wide variation in capacitance over temperature, become resistive at high frequencies. Inductor Selection Inductor selection will be determined by the following (not necessarily in the order of importance); * * * Inductance Rated current value Size requirements
As shown by the previous calculation, the peak inductor current is inversely proportional to the switching frequency and the inductance; the lower the switching frequency or the inductance the higher the peak current. As input voltage increases the peak current also increases. The size of the inductor depends on the requirements of the application. Refer to the Application Circuit and Bill of Material for details. DC resistance (DCR) is also important. While DCR is inversely proportional to size, DCR can represent a significant efficiency loss. Refer to the Efficiency Considerations.
Compensation The MIC23250 is designed to be stable with a 0.47H to 4.7H inductor with a minimum of 2.2F ceramic (X5R) output capacitor. Efficiency Considerations Efficiency is defined as the amount of useful output power, divided by the amount of power supplied.
V xI Efficiency _ % = OUT OUT V xI IN IN x 100
* DC resistance (DCR) The MIC23250 was designed for use with an inductance range from 0.47H to 4.7H. Typically, a 1H inductor is recommended for a balance of transient response, efficiency and output ripple. For faster transient response a 0.47H inductor may be used. For lower output ripple, a 4.7H is recommended. Maximum current ratings of the inductor are generally December 2007
Maintaining high efficiency serves two purposes. It reduces power dissipation in the power supply, reducing the need for heat sinks and thermal design considerations and it reduces consumption of current for battery powered applications. Reduced current draw from a battery increases the devices operating time and is critical in hand held devices. There are two types of losses in switching converters; DC losses and switching losses. DC losses are simply the power dissipation of I2R. Power is dissipated in the high side switch during the on cycle. Power loss is equal to the high side MOSFET RDSON multiplied by the Switch Current squared. During the off cycle, the low side N-channel MOSFET conducts, also dissipating power. Device operating current also reduces efficiency. The product of the quiescent (operating) current and the supply voltage is another DC loss. The current required driving the gates on and off at a constant 4MHz frequency and the switching transitions make up the switching losses.
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Efficiency V OUT = 1.8V
100 80 60 40 20 0 0.1 VIN = 2.7V VIN = 3.6V VIN = 3.3V
MIC23250 comparator turns the PMOS off for a minimum-off-time until the output drops below the threshold. The NMOS acts as an ideal rectifier that conducts when the PMOS is off. Using a NMOS switch instead of a diode allows for lower voltage drop across the switching device when it is on. The asynchronous switching combination between the PMOS and the NMOS allows the control loop to work in discontinuous mode for light load operations. In discontinuous mode, the MIC23250 works in pulse frequency modulation (PFM) to regulate the output. As the output current increases, the off-time decreases, thus providing more energy to the output. This switching scheme improves the efficiency of MIC23250 during light load currents by only switching when it is needed. As the load current increases, the MIC23250 goes into continuous conduction mode (CCM) and switches at a frequency centered at 4MHz. The equation to calculate the load when the MIC23250 goes into continuous conduction mode may be approximated by the following formula:
VOUT = 1.8V L = 1H 1 10 100 LOAD (mA) 1000
The Figure above shows an efficiency curve. From no load to 100mA, efficiency losses are dominated by quiescent current losses, gate drive and transition losses. By using the Hyper Light LoadTM mode the MIC23250 is able to maintain high efficiency at low output currents. Over 100mA, efficiency loss is dominated by MOSFET RDSON and inductor losses. Higher input supply voltages will increase the Gate-to-Source threshold on the internal MOSFETs, thereby reducing the internal RDSON. This improves efficiency by reducing DC losses in the device. All but the inductor losses are inherent to the device. In which case, inductor selection becomes increasingly critical in efficiency calculations. As the inductors are reduced in size, the DC resistance (DCR) can become quite significant. The DCR losses can be calculated as follows: L_Pd = IOUT2 x DCR From that, the loss in efficiency due to inductor resistance can be calculated as follows: VOUT x I OUT Efficiency _ Loss = 1 - V OUT x I OUT + L _ PD x 100
V - VOUT x D I LOAD = IN 2L x f As shown in the previous equation, the load at which MIC23250 transitions from Hyper Light LoadTM mode to PWM mode is a function of the input voltage (VIN), output voltage (VOUT), duty cycle (D), inductance (L) and frequency (f). This is illustrated in the graph below. Since the inductance range of MIC23250 is from 0.47H to 4.7H, the device may then be tailored to enter Hyper Light LoadTM mode or PWM mode at a specific load current by selecting the appropriate inductance. For example, in the graph below, when the inductance is 4.7H the MIC23250 will transition into PWM mode at a load of approximately 4mA. Under the same condition, when the inductance is 1H, the MIC23250 will transition into PWM mode at approximately 70mA.
Switching Frequency vs. Output Current
L = 4.7H
Efficiency loss due to DCR is minimal at light loads and gains significance as the load is increased. Inductor selection becomes a trade-off between efficiency and size in this case.
10
4MHz
Hyper Light Load ModeTM The MIC23250 uses a minimum on and off time proprietary control loop (patented by Micrel). When the output voltage falls below the regulation threshold, the error comparator begins a switching cycle that turns the PMOS on and keeps it on for the duration of the minimumon-time. This increases the output voltage. If the output voltage is over the regulation threshold, then the error
1 L = 1H L = 2.2H 0.1 VIN = 3.6V VOUT = 1.8V COUT = 4.7F 10 100 1000 OUTPUT CURRENT (mA)
0.01 1
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MIC23250 Typical Application Circuit (Fixed 1.575V, 1.8V)
Bill of Materials
Item C1, C2, C3 C4 Part Number C1608X5R0J476K VJ0603Y103KXXAT LQM21PN1R0M00 LQH32CNR1R0M33 L1, L2 LQM31P1R0M00 GFL251812T LQM31PNR47M00 MIPF2520D1R5 U1 MIC23250-GFHYMT Manufacturer TDK(1) Vishay
(2) (3) (3)
Description 4.7F Ceramic Capacitor, 6.3V, X5R, Size 0603 0.01F Ceramic Capacitor, 25V, X7R, Size 0603 1H, 0.8A, 190m, L2mm x W1.25mm x H0.5mm 1H, 1A, 60m, L3.2mm x W2.5mm x H2.0mm 1H, 1.2A, 120m, L3.2mm x W1.6mm x H0.95mm 1H, 0.8A, 100m, L2.5mm x W1.8mm x H1.35mm 0.47H, 1.4A, 80m, L3.2mm x W1.6mm x H0.85mm 1.5H, 1.5A, 70m, L2.5mm x W2mm x H1.0mm 4MHz Dual 400mA Buck Regulator with Hyper Light LoadTM Mode
Qty 3 1
Murata Murata
Murata(3) TDK(1) Murata(3) FDK
(4)
2
Micrel, Inc.
(5)
1
Notes: 1. TDK: www.tdk.com 2. Vishay: www.vishay.com 3. Murata: www.murata.com 4. FDK: www.fdk.co.jp 5. Micrel, Inc: www.micrel.com
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PCB Layout Recommendations
Top Layer
Bottom Layer
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Package Information
10-Pin 2mm x 2mm Thin MLF (MT)
(R)
MICREL, INC. 2180 FORTUNE DRIVE SAN JOSE, CA 95131 USA
TEL +1 (408) 944-0800 FAX +1 (408) 474-1000 WEB http://www.micrel.com
The information furnished by Micrel in this data sheet is believed to be accurate and reliable. However, no responsibility is assumed by Micrel for its use. Micrel reserves the right to change circuitry and specifications at any time without notification to the customer. Micrel Products are not designed or authorized for use as components in life support appliances, devices or systems where malfunction of a product can reasonably be expected to result in personal injury. Life support devices or systems are devices or systems that (a) are intended for surgical implant into the body or (b) support or sustain life, and whose failure to perform can be reasonably expected to result in a significant injury to the user. A Purchaser's use or sale of Micrel Products for use in life support appliances, devices or systems is a Purchaser's own risk and Purchaser agrees to fully indemnify Micrel for any damages resulting from such use or sale. (c) 2007 Micrel, Incorporated.
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